Real and complex spectral shaping for spectral masks improvements

ABSTRACT

An integrated circuit radio transceiver and method therefor includes an integrated circuit radio transceiver operable to provide specified gain levels and transmit path filter responses to correspond with a selected power spectral density mask. Changes in gain may be provided solely digital gain changes or may include analog gain module gain changes. A transmitter selects from one of at least three masks to reduce or eliminate spectral regrowth out of band to satisfy EVM requirements. Non-symmetric masks may also be selected for special circumstances to prevent out of band spectral regrowth. Additionally, pre-distortion settings are applied to in-band frequencies to correspond to the selected PSD mask.

BACKGROUND

1. Technical Field

The present invention relates to wireless communications and, moreparticularly, to circuitry for wireless communications.

2. Related Art

Communication systems are known to support wireless and wire linedcommunications between wireless and/or wire lined communication devices.Such communication systems range from national and/or internationalcellular telephone systems to the Internet to point-to-point in-homewireless networks. Each type of communication system is constructed, andhence operates, in accordance with one or more communication standards.For instance, wireless communication systems may operate in accordancewith one or more standards, including, but not limited to, IEEE 802.11,Bluetooth, advanced mobile phone services (AMPS), digital AMPS, globalsystem for mobile communications (GSM), code division multiple access(CDMA), local multi-point distribution systems (LMDS),multi-channel-multi-point distribution systems (MMDS), and/or variationsthereof.

Depending on the type of wireless communication system, a wirelesscommunication device, such as a cellular telephone, two-way radio,personal digital assistant (PDA), personal computer (PC), laptopcomputer, home entertainment equipment, etc., communicates directly orindirectly with other wireless communication devices. For directcommunications (also known as point-to-point communications), theparticipating wireless communication devices tune their receivers andtransmitters to the same channel or channels (e.g., one of a pluralityof radio frequency (RF) carriers of the wireless communication system)and communicate over that channel(s). For indirect wirelesscommunications, each wireless communication device communicates directlywith an associated base station (e.g., for cellular services) and/or anassociated access point (e.g., for an in-home or in-building wirelessnetwork) via an assigned channel. To complete a communication connectionbetween the wireless communication devices, the associated base stationsand/or associated access points communicate with each other directly,via a system controller, via a public switch telephone network (PSTN),via the Internet, and/or via some other wide area network.

Each wireless communication device includes a built-in radio transceiver(i.e., receiver and transmitter) or is coupled to an associated radiotransceiver (e.g., a station for in-home and/or in-building wirelesscommunication networks, RF modem, etc.). As is known, the transmitterincludes a data modulation stage, one or more intermediate frequencystages, and a power amplifier stage. The data modulation stage convertsraw data into baseband signals in accordance with the particularwireless communication standard. The one or more intermediate frequencystages mix the baseband signals with one or more local oscillations toproduce RF signals. The power amplifier stage amplifies the RF signalsprior to transmission via an antenna.

Typically, the data modulation stage is implemented on a basebandprocessor chip, while the intermediate frequency (IF) stages and poweramplifier stage are implemented on a separate radio processor chip.Historically, radio integrated circuits have been designed usingbi-polar circuitry, allowing for large signal swings and lineartransmitter component behavior. Therefore, many legacy basebandprocessors employ analog interfaces that communicate analog signals toand from the radio processor.

Typically, a digital processor produces outgoing digital signals thatare converted to an analog form, amplified, filtered, and poweramplified prior to transmission. One problem, though, is that themodules in an analog transmit path often create phase and or amplitudedistortion that, in turn, introduces other anomalies such as spectralregrowth. It is known to provide pre-distortion compensation for asignal that is being conducted through the analog transmit path and thenpower amplified and transmitted. Such pre-distortion compensation, doesnot always provide compensation that is optimal thus resulting in theanomalies including spectral regrowth.

SUMMARY OF THE INVENTION

The present invention is directed to apparatus and methods of operationthat are further described in the following Brief Description of theDrawings, the Detailed Description of the Invention, and the claims.Other features and advantages of the present invention will becomeapparent from the following detailed description of the invention madewith reference to the accompanying drawings.

BRIEF DESCRIPTION OF THE DRAWINGS

A better understanding of the present invention can be obtained when thefollowing detailed description of the preferred embodiment is consideredwith the following drawings, in which:

FIG. 1 is a schematic block diagram illustrating a wirelesscommunication device that includes a host device and an associatedradio;

FIG. 2 is a schematic block diagram illustrating a wirelesscommunication host device and an associated radio;

FIG. 3 is a schematic block diagram illustrating a wirelesscommunication device that includes the host device and an associatedradio in an alternate embodiment;

FIG. 4 is a functional block diagram of a wireless transceiver transmitpath according to one embodiment of the invention;

FIG. 5 is a functional block diagram of a wireless transmitter operableto provide gain based compensation and desired filter responses tocorrespond to a selected PSD mask according to one embodiment of theinvention;

FIG. 6 is an exemplary table that illustrates a mapping betweenspecified signal shaping schemes in relation to specified channels andsub-carriers to satisfy a PSD mask according to one embodiment of theinvention;

FIG. 7 is a signal diagram that illustrates an exemplary mask inrelation to a single channel modulated signal according to oneembodiment of the invention in which equal power is applied to theentire spectrum of the modulated signal;

FIG. 8 is a signal diagram that illustrates an exemplary mask inrelation to a plurality of sub-carriers of a modulated signal accordingto one embodiment of the invention in which equal power is applied tothe entire spectrum of the modulated signal;

FIG. 9 is a signal diagram that illustrates exemplary signal shaping inrelation to a single channel modulated signal according to oneembodiment of the invention in which less power is applied to thefrequencies farthest from the center frequency of the modulated signaland the most power is applied to the frequencies proximate to the centerfrequency;

FIG. 10 is a signal diagram that illustrates exemplary signal shaping inrelation to a plurality of sub-carriers of a modulated signal accordingto one embodiment of the invention in which less power is applied to thefrequencies farthest from the center frequency of the modulated signaland the most power is applied to the frequencies proximate to the centerfrequency;

FIG. 11 is a signal diagram that illustrates exemplary signal shaping inrelation to a single channel modulated signal according to oneembodiment of the invention in which no power is applied to thefrequencies farthest from the center frequency of the modulated signaland the most power is applied to the frequencies proximate to the centerfrequency;

FIG. 12 is a signal diagram that illustrates exemplary signal shaping inrelation to a plurality of sub-carriers of a modulated signal accordingto one embodiment of the invention in which no power is applied to thefrequencies farthest from the center frequency of the modulated signaland the most power is applied to the frequencies proximate to the centerfrequency;

FIG. 13 is a signal diagram that illustrates exemplary signal shaping inrelation to a single channel modulated signal according to oneembodiment of the invention in which no power is applied to thefrequencies farthest from the center frequency of the modulated signalat one end of the modulated signal spectrum and in which the PSD mask isnon-symmetric;

FIG. 14 is a signal diagram that illustrates exemplary signal shaping inrelation to a plurality of sub-carriers of a modulated signal accordingto one embodiment of the invention in which no power is applied to thefrequencies farthest from the center frequency of the modulated signalat one end of the modulated signal spectrum and in which the PSD mask isnon-symmetric;

FIG. 15 is a flow chart that illustrates a method for providing desiredpower spectral densities according to one embodiment of the invention;and

FIG. 16 is a functional block diagram of a transmitter that illustratescomplex filtering to provide exemplary signal shaping according to oneembodiment of the invention.

DETAILED DESCRIPTION OF THE DRAWINGS

FIG. 1 is a functional block diagram illustrating a communication systemthat includes circuit devices and network elements and operation thereofaccording to one embodiment of the invention. More specifically, aplurality of network service areas 04, 06 and 08 are a part of a network10. Network 10 includes a plurality of base stations or access points(APs) 12-16, a plurality of wireless communication devices 18-32 and anetwork hardware component 34. The wireless communication devices 18-32may be laptop computers 18 and 26, personal digital assistants 20 and30, personal computers 24 and 32 and/or cellular telephones 22 and 28.The details of the wireless communication devices will be described ingreater detail with reference to FIGS. 2-10.

The base stations or APs 12-16 are operably coupled to the networkhardware component 34 via local area network (LAN) connections 36, 38and 40. The network hardware component 34, which may be a router,switch, bridge, modem, system controller, etc., provides a wide areanetwork (WAN) connection 42 for the communication system 10 to anexternal network element such as WAN 44. Each of the base stations oraccess points 12-16 has an associated antenna or antenna array tocommunicate with the wireless communication devices in its area.Typically, the wireless communication devices 18-32 register with theparticular base station or access points 12-16 to receive services fromthe communication system 10. For direct connections (i.e.,point-to-point communications), wireless communication devicescommunicate directly via an allocated channel.

Typically, base stations are used for cellular telephone systems andlike-type systems, while access points are used for in-home orin-building wireless networks. Regardless of the particular type ofcommunication system, each wireless communication device includes abuilt-in radio and/or is coupled to a radio. Each of the radios may beformed according to one or more standards or protocols including, forexample, I.E.E.E. 802.11(a), (b), (g) or (n). Further one or more of theradios includes circuitry operable to employ the teachings of one ormore embodiments of the invention.

FIG. 2 is a schematic block diagram illustrating a wirelesscommunication host device 18-32 and an associated radio 60. For cellulartelephone hosts, radio 60 is a built-in component. For personal digitalassistants hosts, laptop hosts, and/or personal computer hosts, theradio 60 may be built-in or an externally coupled component.

As illustrated, wireless communication host device 18-32 includes aprocessing module 50, a memory 52, a radio interface 54, an inputinterface 58 and an output interface 56. Processing module 50 and memory52 execute the corresponding instructions that are typically done by thehost device. For example, for a cellular telephone host device,processing module 50 performs the corresponding communication functionsin accordance with a particular cellular telephone standard.

Radio interface 54 allows data to be received from and sent to radio 60.For data received from radio 60 (e.g., inbound data), radio interface 54provides the data to processing module 50 for further processing and/orrouting to output interface 56. Output interface 56 providesconnectivity to an output device such as a display, monitor, speakers,etc., such that the received data may be displayed. Radio interface 54also provides data from processing module 50 to radio 60. Processingmodule 50 may receive the outbound data from an input device such as akeyboard, keypad, microphone, etc., via input interface 58 or generatethe data itself. For data received via input interface 58, processingmodule 50 may perform a corresponding host function on the data and/orroute it to radio 60 via radio interface 54.

Radio 60 includes a host interface 62, a digital receiver processingmodule 64, an analog-to-digital converter 66, a filtering/gain module68, a down-conversion module 70, a low noise amplifier 72, a receiverfilter module 71, a transmitter/receiver (Tx/Rx) switch module 73, alocal oscillation module 74, a memory 75, a digital transmitterprocessing module 76, a digital-to-analog converter 78, a filtering/gainmodule 80, an up-conversion module 82, a power amplifier 84, atransmitter filter module 85, and an antenna 86 operatively coupled asshown. The antenna 86 is shared by the transmit and receive paths asregulated by the Tx/Rx switch module 73. The antenna implementation willdepend on the particular standard to which the wireless communicationdevice is compliant.

Digital receiver processing module 64 and digital transmitter processingmodule 76, in combination with operational instructions stored in memory75, execute digital receiver functions and digital transmitterfunctions, respectively. The digital receiver functions include, but arenot limited to, demodulation, constellation demapping, decoding, and/ordescrambling. The digital transmitter functions include, but are notlimited to, scrambling, encoding, constellation mapping, and modulation.Digital receiver and transmitter processing modules 64 and 76,respectively, may be implemented using a shared processing device,individual processing devices, or a plurality of processing devices.Such a processing device may be a microprocessor, micro-controller,digital signal processor, microcomputer, central processing unit, fieldprogrammable gate array, programmable logic device, state machine, logiccircuitry, analog circuitry, digital circuitry, and/or any device thatmanipulates signals (analog and/or digital) based on operationalinstructions.

Memory 75 may be a single memory device or a plurality of memorydevices. Such a memory device may be a read-only memory, random accessmemory, volatile memory, non-volatile memory, static memory, dynamicmemory, flash memory, and/or any device that stores digital information.Note that when digital receiver processing module 64 and/or digitaltransmitter processing module 76 implements one or more of its functionsvia a state machine, analog circuitry, digital circuitry, and/or logiccircuitry, the memory storing the corresponding operational instructionsis embedded with the circuitry comprising the state machine, analogcircuitry, digital circuitry, and/or logic circuitry. Memory 75 stores,and digital receiver processing module 64 and/or digital transmitterprocessing module 76 executes, operational instructions corresponding toat least some of the functions illustrated herein.

In operation, radio 60 receives outbound data 94 from wirelesscommunication host device 18-32 via host interface 62. Host interface 62routes outbound data 94 to digital transmitter processing module 76,which processes outbound data 94 in accordance with a particularwireless communication standard or protocol (e.g., IEEE 802.11(a), IEEE802.11b, Bluetooth, etc.) to produce digital transmission formatted data96. Digital transmission formatted data 96 will be a digital basebandsignal or a digital low IF signal, where the low IF typically will be inthe frequency range of one hundred kilohertz to a few megahertz.

Digital-to-analog converter 78 converts digital transmission formatteddata 96 from the digital domain to the analog domain. Filtering/gainmodule 80 filters and/or adjusts the gain of the analog baseband signalprior to providing it to up-conversion module 82. Up-conversion module82 directly converts the analog baseband signal, or low IF signal, intoan RF signal based on a transmitter local oscillation 83 provided bylocal oscillation module 74. Power amplifier 84 amplifies the RF signalto produce an outbound RF signal 98, which is filtered by transmitterfilter module 85. The antenna 86 transmits outbound RF signal 98 to atargeted device such as a base station, an access point and/or anotherwireless communication device.

Radio 60 also receives an inbound RF signal 88 via antenna 86, which wastransmitted by a base station, an access point, or another wirelesscommunication device. The antenna 86 provides inbound RF signal 88 toreceiver filter module 71 via Tx/Rx switch module 73, where Rx filtermodule 71 band pass filters inbound RF signal 88. The Rx filter module71 provides the filtered RF signal to low noise amplifier 72, whichamplifies inbound RF signal 88 to produce an amplified inbound RFsignal. Low noise amplifier 72 provides the amplified inbound RF signalto down-conversion module 70, which directly converts the amplifiedinbound RF signal into an inbound low IF signal or baseband signal basedon a receiver local oscillation 81 provided by local oscillation module74. Down-conversion module 70 provides the inbound low IF signal orbaseband signal to filtering/gain module 68. Filtering/gain module 68may be implemented in accordance with the teachings of the presentinvention to filter and/or attenuate the inbound low IF signal or theinbound baseband signal to produce a filtered inbound signal.

Analog-to-digital converter 66 converts the filtered inbound signal fromthe analog domain to the digital domain to produce digital receptionformatted data 90. Digital receiver processing module 64 decodes,descrambles, demaps, and/or demodulates digital reception formatted data90 to recapture inbound data 92 in accordance with the particularwireless communication standard being implemented by radio 60. Hostinterface 62 provides the recaptured inbound data 92 to the wirelesscommunication host device 18-32 via radio interface 54.

As one of average skill in the art will appreciate, the wirelesscommunication device of FIG. 2 may be implemented using one or moreintegrated circuits. For example, the host device may be implemented ona first integrated circuit, while digital receiver processing module 64,digital transmitter processing module 76 and memory 75 may beimplemented on a second integrated circuit, and the remaining componentsof radio 60, less antenna 86, may be implemented on a third integratedcircuit. As an alternate example, radio 60 may be implemented on asingle integrated circuit. As yet another example, processing module 50of the host device and digital receiver processing module 64 and digitaltransmitter processing module 76 may be a common processing deviceimplemented on a single integrated circuit.

Memory 52 and memory 75 may be implemented on a single integratedcircuit and/or on the same integrated circuit as the common processingmodules of processing module 50, digital receiver processing module 64,and digital transmitter processing module 76. As will be described, itis important that accurate oscillation signals are provided to mixersand conversion modules. A source of oscillation error is noise coupledinto oscillation circuitry through integrated circuitry biasingcircuitry. One embodiment of the present invention reduces the noise byproviding a selectable pole low pass filter in current mirror devicesformed within the one or more integrated circuits.

Local oscillation module 74 includes circuitry for adjusting an outputfrequency of a local oscillation signal provided from module 74. Localoscillation module 74 receives a frequency correction input that it usesto adjust an output local oscillation signal to produce a frequencycorrected local oscillation signal output. While local oscillationmodule 74, up-conversion module 82 and down-conversion module 70 areimplemented to perform direct conversion between baseband and RF, it isunderstood that the principles herein may also be applied readily tosystems that implement an intermediate frequency conversion step at alow intermediate frequency.

FIG. 3 is a schematic block diagram illustrating a wirelesscommunication device that includes the host device 18-32 and anassociated radio 60. For cellular telephone hosts, the radio 60 is abuilt-in component. For personal digital assistants hosts, laptop hosts,and/or personal computer hosts, the radio 60 may be built-in or anexternally coupled component.

As illustrated, the host device 18-32 includes a processing module 50,memory 52, radio interface 54, input interface 58 and output interface56. The processing module 50 and memory 52 execute the correspondinginstructions that are typically done by the host device. For example,for a cellular telephone host device, the processing module 50 performsthe corresponding communication functions in accordance with aparticular cellular telephone standard.

The radio interface 54 allows data to be received from and sent to theradio 60. For data received from the radio 60 (e.g., inbound data), theradio interface 54 provides the data to the processing module 50 forfurther processing and/or routing to the output interface 56. The outputinterface 56 provides connectivity to an output display device such as adisplay, monitor, speakers, etc., such that the received data may bedisplayed. The radio interface 54 also provides data from the processingmodule 50 to the radio 60. The processing module 50 may receive theoutbound data from an input device such as a keyboard, keypad,microphone, etc., via the input interface 58 or generate the dataitself. For data received via the input interface 58, the processingmodule 50 may perform a corresponding host function on the data and/orroute it to the radio 60 via the radio interface 54.

Radio 60 includes a host interface 62, a baseband processing module 100,memory 65, a plurality of radio frequency (RF) transmitters 106-110, atransmit/receive (T/R) module 114, a plurality of antennas 81-85, aplurality of RF receivers 118-120, and a local oscillation module 74.The baseband processing module 100, in combination with operationalinstructions stored in memory 65, executes digital receiver functionsand digital transmitter functions, respectively. Moreover, basebandprocessing module 100 further includes, in the described embodiment, afiltering/gain control module 101. Filtering/gain control module 101 isoperable, in one embodiment, to define power spectral density masks thathave specified shapes for power and gain across the bandwidth channelfor different modulation schemes including orthogonal frequency divisionmultiplexing (OFDM).

The digital receiver functions include, but are not limited to, digitalintermediate frequency to baseband conversion, demodulation,constellation demapping, decoding, de-interleaving, fast Fouriertransform, cyclic prefix removal, space and time decoding, and/ordescrambling. The digital transmitter functions include, but are notlimited to, scrambling, encoding, interleaving, constellation mapping,modulation, inverse fast Fourier transform, cyclic prefix addition,space and time encoding, and digital baseband to IF conversion. Thebaseband processing module 100 may be implemented using one or moreprocessing devices. Such a processing device may be a microprocessor,micro-controller, digital signal processor, microcomputer, centralprocessing unit, field programmable gate array, programmable logicdevice, state machine, logic circuitry, analog circuitry, digitalcircuitry, and/or any device that manipulates signals (analog and/ordigital) based on operational instructions. The memory 65 may be asingle memory device or a plurality of memory devices. Such a memorydevice may be a read-only memory, random access memory, volatile memory,non-volatile memory, static memory, dynamic memory, flash memory, and/orany device that stores digital information. Note that when the basebandprocessing module 100 implements one or more of its functions via astate machine, analog circuitry, digital circuitry, and/or logiccircuitry, the memory storing the corresponding operational instructionsis embedded with the circuitry comprising the state machine, analogcircuitry, digital circuitry, and/or logic circuitry.

In operation, the radio 60 receives outbound data 94 from the hostdevice via the host interface 62. The baseband processing module 100receives the outbound data 94 and, based on a mode selection signal 102,produces one or more outbound symbol streams 104. The mode selectionsignal 102 will indicate a particular mode of operation that iscompliant with one or more specific modes of the various IEEE 802.11standards. For example, the mode selection signal 102 may indicate afrequency band of 2.4 GHz, a channel bandwidth of 20 or 22 MHz and amaximum bit rate of 54 megabits-per-second. In this general category,the mode selection signal will further indicate a particular rateranging from 1 megabit-per-second to 54 megabits-per-second. Inaddition, the mode selection signal will indicate a particular type ofmodulation, which includes, but is not limited to, Barker CodeModulation, BPSK, QPSK, CCK, 16 QAM and/or 64 QAM. The mode selectionsignal 102 may also include a code rate, a number of coded bits persubcarrier (NBPSC), coded bits per OFDM symbol (NCBPS), and/or data bitsper OFDM symbol (NDBPS). The mode selection signal 102 may also indicatea particular channelization for the corresponding mode that provides achannel number and corresponding center frequency. The mode selectionsignal 102 may further indicate a power spectral density mask value anda number of antennas to be initially used for a MIMO communication.

The baseband processing module 100, based on the mode selection signal102 produces one or more outbound symbol streams 104 from the outbounddata 94. For example, if the mode selection signal 102 indicates that asingle transmit antenna is being utilized for the particular mode thathas been selected, the baseband processing module 100 will produce asingle outbound symbol stream 104. Alternatively, if the mode selectionsignal 102 indicates 2, 3 or 4 antennas, the baseband processing module100 will produce 2, 3 or 4 outbound symbol streams 104 from the outbounddata 94.

Depending on the number of outbound symbol streams 104 produced by thebaseband processing module 100, a corresponding number of the RFtransmitters 106-110 will be enabled to convert the outbound symbolstreams 104 into outbound RF signals 112. In general, each of the RFtransmitters 106-110 includes a digital filter and upsampling module, adigital-to-analog conversion module, an analog filter module, afrequency up conversion module, a power amplifier, and a radio frequencyband pass filter. The RF transmitters 106-110 provide the outbound RFsignals 112 to the transmit/receive module 114, which provides eachoutbound RF signal to a corresponding antenna 81-85.

When the radio 60 is in the receive mode, the transmit/receive module114 receives one or more inbound RF signals 116 via the antennas 81-85and provides them to one or more RF receivers 118-122. The RF receiver118-122 converts the inbound RF signals 116 into a corresponding numberof inbound symbol streams 124. The number of inbound symbol streams 124will correspond to the particular mode in which the data was received.The baseband processing module 100 converts the inbound symbol streams124 into inbound data 92, which is provided to the host device 18-32 viathe host interface 62.

As one of average skill in the art will appreciate, the wirelesscommunication device of FIG. 3 may be implemented using one or moreintegrated circuits. For example, the host device may be implemented ona first integrated circuit, the baseband processing module 100 andmemory 65 may be implemented on a second integrated circuit, and theremaining components of the radio 60, less the antennas 81-85, may beimplemented on a third integrated circuit. As an alternate example, theradio 60 may be implemented on a single integrated circuit. As yetanother example, the processing module 50 of the host device and thebaseband processing module 100 may be a common processing deviceimplemented on a single integrated circuit. Further, the memory 52 andmemory 65 may be implemented on a single integrated circuit and/or onthe same integrated circuit as the common processing modules ofprocessing module 50 and the baseband processing module 100.

Finally, is should be mentioned that digital processing module 76 ofFIG. 2 and baseband processing module 100 of FIG. 3 are, in embodiment,of the invention, operable to provide pre-distortion compensation basedupon an analog transmit path gain to provide optimal compensation asgain levels of the analog transmit path are changed based uponoperational demands and/or conditions. The radio transceivers of FIGS. 2and 3 and the circuitry and methods described below may further beimplemented within the wireless transceivers of the network of FIG. 1.

FIG. 4 is a functional block diagram of a wireless transceiver transmitpath 250 according to one embodiment of the invention. Though notspecifically shown here, a baseband or other digital processor typicallyproduces outgoing digital data that is received and processed by aplurality of known digital processing blocks or modules (collectively, adigital transmit path 252) that includes modules such as symbol mappingmodule 254, one or more modules 258 that collectively perform spreading,interleaving, scrambling, coding and pulse shaping and a pre-distortioncompensation module 262. It should be understood that modules of thedigital transmit path of the comprise digital functionality that performone or more specified functions to create a digital signal thateventually is converted to a traditional analog signal form forprocessing and transmission from a transmit path. Moreover, the modulesand functionality listed for the digital transmit path 252 are exemplaryand may be changed according to specific design requirements.Specifically, for example, some of the functionality may be removed orother functionality, such as up-sampling modules and decimation modulesto modify a sample rate of the digital data may be included.

Pre-distortion compensation module 262 is operable to introduce phaseand/or magnitude compensation to a received digital signal to compensatefor downstream analog transmit path distortion. In the embodiment ofFIG. 4, pre-distortion compensation module 262 is operable to provide aplurality of compensation settings (or pre-distortion curves) based upona corresponding plurality of gain settings within the analog transmitpath. Generally, a pre-distortion curve is determined for each analogtransmit path gain setting. The pre-distortion curves thus define thepre-distortion gain settings that are applied to a digital signal topre-compensate for downstream distortion that will be introduced in theanalog transmit path.

Additionally, a digital gain module 266 typically provides a specifiedamount of digital gain to the outgoing digital signals. Here, digitalgain module 266 produces a digital gain based upon a received digitalgain control signal produced by digital gain control 270 that includeslogic for adjusting the digital gain as will be described in greaterdetail below. The outgoing digital signal produced by digital gainmodule 266 is then produced to a digital-to-analog conversion module274. As may be seen, digital-to-analog conversion module 274 is alsocoupled to receive a gain control signal from a digital-to-analog gaincontrol module 276. Digital-to-analog gain control module 276 isoperable to adjust a gain of digital-to-analog conversion module 274which is therefore operable to produce an outgoing analog baseband orintermediate frequency band signal for processing to and by an analogtransmit path 278 having an adjustable gain level. While these gainsettings technically are in the analog transmit path, they are treatedseparately from all other gain settings in the analog transmit pathbecause digital-to-analog conversion module 274 effectively adjusts thegain of the input digital signal and therefore does not affect theanalog transmit path distortion levels or linearity. Accordingly,references herein to adjust a digital gain specifically includeadjusting the gain of digital-to-analog conversion module 274.

Analog transmit path 278 includes filtering and gain module 282,upconversion module 286, filtering and gain module 290 and poweramplifier 294. In the described embodiment, filtering and gain module282, filtering and gain module 290 and power amplifier 294 are eachoperably disposed to receive gain control signals from analog gaincontrol module 298. Moreover, the modules may comprise a plurality ofmodules. For example, in one embodiment, filtering and gain module 290may comprise a plurality of high-pass variable gain amplifiers thatprovide amplification and high-pass filtering for an outgoing radiofrequency signal that has already be upconverted from a basebandfrequency signal or from an intermediate frequency signal. Analog gaincontrol 298 is therefore operable to provide at least one of gaincontrol and filter control to a plurality of filtering and gain controlmodules in the analog transmit path 278.

As may also be seen, the transmit path of the transceiver of FIG. 4further includes a signal shaping logic module 272 which is operable toselect and produce an indication of a selected signal shaping scheme.The indication or control information is produced to prompt the variousdigital and analog gain and filtering elements of the transmit path toproduce a gain/power or filter response that corresponds to the selectedsignal shaping scheme. In the embodiment of FIG. 4, the selected signalshaping scheme is produced to digital control module 270 of digitaltransmit path 252 and to analog gain and filter control module 298 ofanalog transmit path 278. Based on the received selected mask controlsignal, analog gain and filter control module 298 modifies gain orsignal magnitudes of one or more gain elements in the analog transmitpath 278 as well as modifying filter response shaping of one or morefilters.

In the described embodiment of the invention, the filters, especiallythe low pass filter(s), of the analog transmit path 278 have selectablefilter responses to support a plurality of filter responses for adesired signal frequency spectrum or range. Moreover, high frequencyfiltering is performed by filtering and gain module 290 while lowfrequency filtering is performed by filtering and gain module 282. Assuch, in the embodiment of FIG. 4, analog gain and filter control module298 is operable to produce a non-symmetric shaped signal response byseparately controlling low frequency and high frequency gain as well asfiltering. Analog gain control 298 is operable to provide at least oneof gain control and filter control to a plurality of filtering and gaincontrol modules in the analog transmit path 278. In general, analog gaincontrol 298 is operable to generate control signal to support signalshaping for modules in which such signal shaping may be performedwithout introducing additional non-linearity or other problems with theoutgoing signal. For example, while analog gain control 298 is operableto provide gain level setting to each gain module or element of theanalog transmit path 278, analog gain control 298 may only providecontrol signals to filter and gain elements prior to the power amplifierof the analog transmit path 278. For example, signal shaping controlcommands may be sent to only one of filtering and gain module 282 and290 or to both but not to power amplifier 294. With respect to FIG. 5,which is discussed in greater detail below, signal shaping controlcommands are not sent to power amplification module 336 but can be sentto at least one of filter and gain modules 308 and 324.

One aspect of the embodiments of the invention is the use of selectedsignal shaping schemes to satisfy error-vector magnitude (EVM)requirements for a given signal type. Depending on the signal type andeven transmission channel, spectral re-growth may violate EVMrequirements. Accordingly, the embodiments of the present inventionselect signal shaping schemes to define power spectral densityrequirements that account for the transmission signal type (andassociated spectral flatness requirements, EVM requirements generallyassociated for a specific transmission signal type (e.g., 802.11(a), (b)or (g)). Additionally, for some signal types, based in part uponassigned signal frequency range, a selected channel for the signal mayhave additional EVM requirements to avoid spectral regrowth withinrestricted bands. Accordingly, signal magnitude, digital and analoggain, and pre-distortion compensation settings are potentially limitedby a selected signal shaping scheme that is used to satisfy signalflatness and EVM requirements whether the signal is a single carriersignal or multiple carrier OFDM signal.

One aspect of the embodiments of the invention includes reducing thegain/power at the frequencies farthest from a center frequency of amodulated signal to the extent allowed by a transmission standard orprotocol corresponding to a signal transmission (hereinafter “signaltype”). Reducing the gain/power at the ends of the modulated signalspectrum (whether a single channel or a plurality of channels for andOFDM modulated signals) reduces out of band spectral regrowth andpotential violation of EVM requirements.

In operation, digital gain control module 270, digital-to-analog gaincontrol module 276 and analog gain and filter control module 298collectively define a total gain of a signal being wirelesslytransmitted from an antenna operably disposed to receive the output ofpower amplifier 294. This total gain is based, at least in part, on theselected signal shaping scheme. Pre-distortion compensation module 262,however, produces a pre-compensation adjustment to an outgoing digitalsignal based upon a specified analog transmit path gain level of one ormore gain levels specified by analog gain and filter control 298. Thereferences herein to “specified gain levels” for the analog transmitpath refer to analog transmit path gain settings for which a specificpre-distortion compensation setting is generated by pre-distortioncompensation module 262.

In a preferred embodiment, the specified gain levels of the analogtransmit path are discrete gain settings with a constant step size. Inan alternate and equivalent embodiment, however, pre-distortion settingsare defined for analog transmit path gain settings that fall within aspecified range. One aspect of the embodiments of the present inventionis that digital gain control 270 is operable to provide digital gainadjustments to supplement a current analog transmit path gain to providea desired total gain. Thus, if a new total desired gain is one that canbe achieved by changing only the digital gain, then only the digitalgain is changed and a current pre-distortion compensation setting is notmodified to maintain effectiveness.

Typically, however, a limit is specified for total digital gain changesbecause of performance limitations of the digital to analog conversionmodule 274. Thus, if the gain adjustment exceeds a maximum valueallowed, the gain of the analog transmit path 278 is changed to beproximate to the desired total gain (within a tolerance or range) andthen the digital gain is adjusted to provide the desired total gain.

One aspect of the embodiments of the invention is that thepre-distortion compensation module 262 is operable to produce aplurality of pre-distortion curves that define pre-distortion settingsthat correspond to a corresponding plurality of specified gain levels ofthe analog transmit path 278. Alternatively, the pre-distortion settingscorrespond to gain settings of a subset of the analog gain modules inthe transmit path. In one specific embodiment, the pre-distortioncompensation settings correspond to gain settings of one specific modulein analog transmit path 278. For example, a plurality of pre-distortionsettings may be defined for a corresponding plurality of gain settingsof power amplifier 274. This embodiment is advantageous in that powerfrom the power amplifier is not wasted for lower gain settings. Incontrast, many prior art systems keep the power amplifier at a high ormaximum power level while modifying other gain modules in the transmitpath since changing the power amplifier gain level is most likely torender the single pre-distortion setting less effective.

One additional aspect of the embodiment of FIG. 4 is that the system isoperable to make digital gain adjustments by changing the digital gainwithin digital transmit path 252 and the gain of digital-to-analogconversion module 274. If a gain change is required by either the poweramplifier 294 or any other module in the analog transmit path 278,however, the gain is changed by a specified gain amount or step that hasan associated pre-distortion curve. As such, new pre-distortion settings(based on pre-distortion curve) correspond to the change in the analogtransmit path. Thereafter, the digital gain is adjusted to supplementthe analog transmit path gain, if necessary, to produce the total amountof desired gain.

It should be understood that the transmit path of FIG. 4 is an exemplarytransmit path. A radio transceiver formed according on one embodiment ofthe invention may include a plurality of transmit paths for a multiplein multiple out (MIMO) type radio transceiver. Some or even all of themodules of FIG. 4 may be duplicated for each transmit path according todesign implementation. Such a MIMO transceiver may, for example, eachtransmit one or more sub-carriers of a given OFDM signal. Each of thefiltering and gain modules 282 and 290, as well as digital gain control270 and digital-to-analog gain control module 276, may jointly berepresented as module 101 of FIG. 3, and may operate to support adefined shaped signal response.

FIG. 5 is a functional block diagram of a wireless transmitter operableto provide gain based compensation according to one embodiment of theinvention. As may be seen, a digital processor 302 is operably disposedto produce an outgoing digital signal to a digital to analog converter304 which then produces an analog transmit path signal based on theoutgoing digital signal to a filtering and gain module 308. Filteringand gain module 308 then produces an amplified and filtered analogtransmit path signal at one of a baseband or intermediate frequency.

The output of filtering and gain module 308 is based upon the receivedanalog transmit path signal as well as a filter control signal 312 and again control signal 316 received from logic or, as shown here, fromdigital processor 302. The output of filtering and gain module 308 isthen produced to an up-conversion module 320 that is operable to producean up-converted radio frequency signal. The up-converted radio frequencysignal is then produced to filtering and gain module 324. Filtering andgain module 324 then produces and an outgoing amplified and filteredradio frequency signal based on the up-converted radio frequency signaland also based upon a filter control signal 328 and a gain controlsignal 332 to power amplification module 336. Power amplification modulethen amplifies the outgoing amplified and filtered radio frequencysignal based upon a gain control signal 340.

As may be further seen, digital processor 302 further includes analoggain control module 344 operable to specify analog transmit path gainmodule gain settings, pre-distortion compensation module 346 operable toset pre-distortion compensation settings based upon (corresponding to)the analog transmit path gain module gain settings and digital gaincontrol signal 348, and digital gain control module 348 operable tospecify digital gain settings. As may also be seen, digital processor302 produces gain control signals 306 to digital-to-analog conversionmodule 304. These gain level settings are treated as being digital gainlevel changes since, in one embodiment, the gain of the input signal toconversion module 304 is effectively adjusted prior to conversion to ananalog form. As such, these adjustments do not affect distortion that isintroduced in the transmit path. These gain control settings 306 may bedetermined either by analog gain control module 344 or by digital gaincontrol 348. In the described embodiment, they are determined by digitalgain control 348 since, effectively, they are similar to digital gainadjustments in that they do not affect the analog transmit pathdistortion.

Additionally, digital processor 302 further includes signal shapinglogic 350 that is operable to support in band signal shaping to satisfyout of band power spectral mask requirements. Signal shaping logic isoperable to communicate with digital gain control module 348 and analoggain control module 344 to provide signal shaping information. Thissignal shaping information may be in any form including anidentification of selected PSD mask information for one or more PSDmasks to enable gain control modules 344 and 348 to make correspondinggain level determinations to provide signal shaping that corresponds tothe PSD mask information. Accordingly, analog gain control module 344generates gain control signals 332 and 340 based in part on the digitalgain setting and to correspond to a power spectral density of the one ormore PSD masks in addition to filter control signals 312 and 328 tofilter and gain modules 308 and 324 to define an overall PSD mask thatproduces a desired power spectral density.

It should be understood that the transmit path of FIG. 5 is an exemplarytransmit path. A radio transceiver formed according on one embodiment ofthe invention may include a plurality of transmit paths for a multiplein multiple out (MIMO) type radio transceiver. Some or even all of themodules of FIG. 5 may be duplicated for each transmit path according todesign implementation. Such a MIMO transceiver may, for example, eachtransmit one or more sub-carriers of a given OFDM signal. Each of thefiltering and gain modules 308 and 324, as well as digital gain control348, provide in band signal shaping similar to filtering and gaincontrol module 101 of FIG. 3, as necessary, to satisfy a defined powerspectral density (PSD) mask.

In operation, digital processor 302, and more particularly, analog gaincontrol module 344 generates gain control signals 316, 332 and 340 tocontrol analog transmit path gain. It should be understood that more orless numbers of gain modules and control lines may be included in atransmit path. Digital processor 302 also generates filter controlsignals 312 and 328 to define response time and pole location of thevarious filters in the analog transmit path. Additionally, digital gaincontrol module 348 adjusts a digital gain of the outgoing digital signalaccording to a desired total transmit path gain. Finally, pre-distortioncompensation 346 produces pre-distortion settings to superimpose on orapply to the outgoing digital signal. Specific operation of the logicfor the pre-distortion compensation and the analog and digital controlis similar to that described above in relation to FIG. 4 as well as willbe described in the discussion of the figures that follow. In general,however, pre-distortion compensation provides a plurality ofpre-distortion curves, that define pre-distortion settings, for acorresponding plurality of analog transmit path gain settings.

In one embodiment, the pre-distortion curves correspond only to gainsettings for power amplifier 336. In another embodiment, thepre-distortion curves correspond to total analog transmit path gainsettings. References herein to analog transmit path gain settingstherefore include both approaches. In operation, digital processor 302selects a new total transmit path gain setting and subsequently adjuststhe digital gain only if the new total transmit path gain is within aspecified threshold or amount from a current analog transmit path gainsetting (either the power amplifier or total transmit path according toembodiment). If not, digital processor 302 is operable to adjust theanalog transmit path gain, apply a corresponding pre-distortioncompensation, and adjust the digital gain if necessary. Suchpre-distortion compensation, however, is preferably performed in view ofa in-band signal shaping that is performed to satisfy an out of band PSDmask requirement.

FIG. 6 is an exemplary table that illustrates a mapping betweenspecified signal shaping schemes in relation to specified channels andsub-carriers to satisfy a PSD mask according to one embodiment of theinvention. As may be seen, each signal shaping scheme has acorresponding carrier/sub-carrier to which the mask can be selectivelyapplied. The mapping defined in table 360 of FIG. 6 represents an asignal shaping scheme that is provided by either just one gain module orby a plurality of gain modules in an analog transmit path in addition togain provided by a digital gain module.

In general, there are many implementation options. For example, in oneembodiment, each modulation signal may have one or more correspondingsignal shaping schemes according to a transmission type or destination.The signal shaping schemes typically will define gain/power for allfrequencies whether in a single carrier or across a plurality ofsub-carriers of an OFDM signal. Alternatively, for an OFDM modulationsignal, each sub-carrier may have a defined signal shaping scheme.

For either approach, a signal shaping scheme may slightly reduce thepower and the frequencies the farthest from a center frequency of amodulated signal or sub-carrier (e.g., 1.5-2.5 dB) or may substantiallyreduce the power (apply zero power) to the frequencies the farthest fromthe center frequency or may apply equal power to all frequencies. In theembodiments in which gain is reduced according to a signal shapingscheme, the most gain/power is applied to the center frequencies orfrequencies proximate to the center frequency of the modulated signal.In one embodiment, power is merely reduced for the outer frequencies. Inanother embodiment, frequencies proximate to the center frequency of thechannel are increased to an amount allowed to not violate a total powerlevel restriction for the channel (including sub-carriers in an OFDMtransmission).

In the embodiment of FIG. 6, it may be seen than signal shaping schemeS₁ or signal shaping scheme S₂ may be selected for either carrier C₁ orsub-carrier SC₁. Without repeating all of the information of exemplarytable 360 of FIG. 6, it also be noted that three different signalshaping schemes S₁, S₂ and S₃ are defined for transmission for carrierC₁. Here, carrier C₁ is a carrier for a single channel. The referencesherein to carriers are for single channels. The signal shaping schememay be selected, for example, based upon a selected transmissionprotocol or signal type for the signal of carrier C1. Similarly, signalshaping scheme S₁, S₂ and S₅ are defined for transmission of a commonplurality of sub-carriers (here SC₁, SC₂, SC₃ and SC₄) of an OFDMmodulation. Thus, it may be seen that, for a given modulated signal(whether single carrier or having a plurality of sub-carriers for anOFDM signal, for example), a plurality of signal shaping schemes may bedefined and selected.

The signal shaping scheme that is selected may be selected based uponthe signal type. For example, FCC restrictions prohibit transmission ofsignals having a frequency of less than approximately 2400 MHz.Accordingly, for channel 1 transmissions of 802.11(b) and 802.11(g) WLANsignals, signal shaping is utilized to prevent spectral regrowth in theprohibited frequency range. In one embodiment, non-symmetric signalshaping is employed in which lower frequency components aresubstantially reduced in gain/power for a specified modulation type thatcorresponds to a transmission protocol (e.g., an 802.11(b)transmission).

As another example, 802.11(a) and 802.11(g) WLAN signals are required tosatisfy certain flatness requirements. Moreover, some standards havestrict EVM requirements while other standards, such as 802.11(b) havemuch more lenient EVM requirements which can often be satisfied withoutthe use of signal shaping schemes that reduce gain/power for specifiedfrequencies.

Because of the channel 1 potential for 802.11(b) and 802.11(g) WLANsignals to generate spectral regrowth in FCC prohibited frequencies, oneembodiment of the invention includes circuitry and/or logic to define atleast one signal shaping scheme that substantially limits gain/powerfarthest from a center frequency of a modulated signal and closest tothe prohibited frequency range. On the other hand, the signal shapingscheme does not substantially limit gain/power for frequencies of themodulated channel farthest from the prohibited frequency range and thusdefines a non-symmetric signal shaping scheme. In one specificimplementation, a specified signal shaping scheme defines differentgain/power spectral densities for the in-phase and quadrature phasebranches of a transmit signal path for specified frequencies.

FIG. 7 is a signal diagram that illustrates an exemplary mask inrelation to a single channel modulated signal according to oneembodiment of the invention in which equal power is applied to theentire spectrum of the modulated signal. As may be seen, mask 370 is onethat corresponds to the modulated signal and only inhibits out of bandsignal frequencies. The signal shaping of FIG. 7 defines a flat shapedin-band response that does not slightly or substantially reduce thegain/power at the ends of the signal spectrum of the channel.

FIG. 8 is a signal diagram that illustrates an exemplary mask inrelation to a plurality of sub-carriers of a modulated signal accordingto one embodiment of the invention in which equal gain/power is appliedto the entire spectrum of the modulated signal. As may be seen, the samesignal shaping of FIG. 7 is selected here wherein gain/power is notreduced for outer frequencies (those farthest from the center frequencyof the modulated channel) and is applied to a plurality of sub-carriersof an OFDM modulated signal. It should be noted that the number ofsub-carriers can be, for example, a large number such as 50.

FIG. 9 is a signal diagram that illustrates exemplary signal shaping inrelation to a single channel modulated signal according to oneembodiment of the invention in which less power is applied to thefrequencies farthest from the center frequency of the modulated signaland the most power is applied to the frequencies proximate to the centerfrequency. More specifically, a shaped signal scheme 372 is applied toreduce the power spectral density for the frequencies farthest from acenter frequency of the modulated signal. The hatched portion at bothends of the modulated in band signal spectrum reflect the inhibitedsignal gain/power. Stated differently, the hatched portion represents aportion of a signal power spectral density that would be present but forthe selected signal shaping scheme. The reduction in the power spectraldensity in these regions is accomplished by either reducing gain or byselecting a filter response (or both) that reduces the power spectraldensity from what would have been realized without the signal shapingscheme.

FIG. 10 is a signal diagram that illustrates exemplary signal shaping inrelation to a plurality of sub-carriers of a modulated signal accordingto one embodiment of the invention in which less power is applied to thefrequencies farthest from the center frequency of the modulated signaland the most power is applied to the frequencies proximate to the centerfrequency. The same mask 372 of FIG. 10 is applied here to an OFDMmodulated signal having a plurality of channels (sub-carriers). As maybe seen, signal shaping scheme 372 produces a similar PSD mask inhibitedsignal even though OFDM modulation is being used for the modulatedsignal.

One aspect shown in relation to FIGS. 9 and 10 is that the amount ofpower spectral density reduction is limited by a required PSD flatnessfor certain signal types. In one embodiment, the required flatnesslimits the variation of a signal relative to a peak value to three dB.Accordingly, for such applications, the selected signal shaping schemeonly reduces the gain/power at the ends of the spectrum of the modulatedsignal by 1.5-2.5 dB of the peak gain/power at the center frequency ofthe modulated signal (whether single channel or OFDM).

FIG. 11 is a signal diagram that illustrates exemplary signal shaping inrelation to a single channel modulated signal according to oneembodiment of the invention in which no power is applied to thefrequencies farthest from the center frequency of the modulated signaland the most power is applied to the frequencies proximate to the centerfrequency. FIG. 12 is a signal diagram that illustrates exemplary signalshaping in relation to a plurality of sub-carriers of a modulated signalaccording to one embodiment of the invention in which no gain/power isapplied to the frequencies farthest from the center frequency of themodulated signal and the most power is applied to the frequenciesproximate to the center frequency.

For both FIGS. 11 and 12, no flatness requirements as shown in relationto FIGS. 9 and 10 limit the amount power spectral density or gainreduction at the ends of the spectrum of the modulated signal.Accordingly, for this signal type, the gain/power for outer mostfrequency components are substantially reduced. In the shown embodimentsof FIGS. 11 and 12, the power spectral densities are reduced to zero. Inother embodiments, the power spectral densities are substantiallyreduced to a value above zero but below a value that would be requiredfor required spectral flatness (e.g., within 1.5-2.5 dB of peak values).

FIG. 13 is a signal diagram that illustrates exemplary signal shaping inrelation to a single channel modulated signal according to oneembodiment of the invention in which no power is applied to thefrequencies farthest from the center frequency of the modulated signalat one end of the modulated signal spectrum and in which the signalshaping is non-symmetric. As may be seen, signal shaping scheme 372 doesnot inhibit the gain/power at the high frequency end of the modulatedsignal spectrum while the gain/power is reduced to zero at the lowfrequency end of the modulated signal spectrum. In 802.11(a) and (g)applications, channel 1 signals that are adjacent to FCC limited signalfrequencies for which interference or spectral regrowth should beavoided to comply with FCC restricted band requirements examples ofmodulated signals for which such in-band signal shaping may be applied.

FIG. 14 is a signal diagram that illustrates exemplary signal shaping inrelation to a plurality of sub-carriers of a modulated signal accordingto one embodiment of the invention in which no power is applied to thefrequencies farthest from the center frequency of the modulated signalat one end of the modulated signal spectrum and in which the PSD mask isnon-symmetric. As may be seen, signal shaping scheme 372 of FIG. 13 isapplied here to the OFDM modulated signal of FIG. 14 wherein on aportion of sub-carrier 1 is inhibited by the signal shaping scheme 372.Accordingly, a non-symmetric power spectral density results not only tothe first sub-carrier (sub-carrier 1) of the modulated signal but alsoin relation to the entire modulated signal as channel 4 is notsymmetrically inhibited in comparison to sub-carrier 1.

FIG. 15 is a flow chart that illustrates a method according to oneembodiment of the invention. Initially, the method includes producing anoutgoing digital signal and, based upon the outgoing digital signal,producing an outgoing continuous waveform radio frequency signal. As apart of producing the outgoing radio frequency signal, the methodincludes selecting a shaped filter response output according to one ofat least three defined signal shaping schemes (step 400).

The three signal shaping schemes include equal gain/power to allfrequencies of a modulated signal, greater power to proximate to thespecified center frequency of the modulated signal than frequencies atthe outer ends of a specified bandwidth of the modulated signal, and nopower to the signal frequencies of the modulated signal to at least oneend of the specified bandwidth. In the described embodiment, the signalshaping scheme is selected based at least in part upon the type ofsignal being transmitted and the corresponding standards or protocolsfor the signal type. For example, different modulation techniques havediffering spectral considerations. Because higher order modulationtechniques having higher data rates create non-constant envelopes andproduce non-linear responses, the in band signal tends to degrade andcan also be more likely to lead to out of band spectral regrowth. Ingeneral, therefore, the methods and circuitry of the embodiments of theinvention provide for selecting and using signal shaping schemes toreduce or eliminate out of band spectral regrowth and for selecting andusing pre-distortion compensation to correct in-band distortions causedby the non-constant envelope and non-linear circuit responses.Accordingly, three basic types of in band signal shaping schemes areimplemented in one embodiment of the invention.

For a first signal type having a first data rate or modulation order,the method includes selecting a signal shaping scheme that results in apower spectral density for which there is equal power to all frequenciesof the modulated signal (step 404). Stated otherwise, equal gain/poweris applied across the modulated signal channel. Thus, the methodincludes evaluating a signal type as a part of selecting and applying asignal shaping scheme that applies equal gain/power to all frequencies.

For a second type of signal having a second data rate or modulationorder, the method includes applying a first maximum allowed gain/powerto the proximate center frequency of the modulated signal and applyingreduced gain/power to frequencies that are a defined distance from thecenter frequency but still in-band of the modulated signal channel (step408). In at least one embodiment, the reduced gain/power is within aspecified amount of the second maximum allowed power. In one specificembodiment, the reduced power spectral density is within 1.5-2.5 dB ofthe first maximum allowed power. In other embodiments, the reducedgain/power ranges from 0 dB to this 1.5-2.5 dB down value relative tothe center frequency gain/power.

For a third type of signal having a third data rate or modulation order,the method includes applying a second maximum allowed power to aproximate center frequency of the modulated signal and applying no powerto frequencies that are a defined distance from the center frequency butstill in-band of the modulated signal channel (step 412). For thisembodiment and for any embodiment that spectral flatness requirementsdon't exist or are relatively lenient, power that is saved by applyingno power or substantially reduced power to the outermost frequencies ofthe modulated signal spectrum may be added to the frequencies proximateto the center most frequency so long as the total transmitted power forthe modulated signal is within the specified amount (whether specifiedby internal logic or communication protocol). Accordingly, the secondmaximum allowed power is greater than the first allowed power to theproximate center frequencies of the modulated signal.

The method of the embodiments of the present invention may thereforeinclude applying the differing amounts of gain/power to variousfrequencies about a center frequency of a modulated signal by modifyingthe filter response and/or amplifier gain level according to whether asignal type is a first type, a second type or a third type.Additionally, the differing amounts of power may also be varied byadjusting at least one digital or analog gain to comply with theselected signal shaping scheme. Additionally, the method includesapplying pre-distortion compensation that complies with the selectedsignal shaping scheme (step 416). For example, the pre-distortioncompensation not only includes digital gain settings, but also selectingin-band frequencies to which the pre-distortion compensation is applied.

An additional aspect of the method of FIG. 15 is that non-symmetricamounts of power or power spectral densities may be achieved using aselected non-symmetric signal shaping scheme for the frequenciesfarthest from the center frequency of the modulated signal (step 420).In one specific embodiment, complex filtering is provided in whichin-phase and quadrature phase branches of a transmit path are filteredwith differing filter responses to produce the non-symmetric powerspectral density response (step 424).

FIG. 16 is a functional block diagram of an exemplary transmitter forwhich complex filtering is provided to create a non-symmetric signalshaping according to one embodiment of the invention. As may be seen,transmitter 500 includes a digital processor 504 that produces in-phase(I) and quadrature phase (Q) digital signal components on correspondingI and Q branches of a transmit path. The in-phase signal components areproduced to a digital to analog converter 508 that produces an analogwaveform signal to a low pass filter 512. The quadrature phase signalcomponents are produced to a digital to analog converter 516 thatproduces an analog waveform signal to a low pass filter 520.

The outputs of filters 512 and 520 are then combined by signal adder 524that produces a combined outgoing analog signal to up-conversion module528. Up-conversion may be implemented in one or more up-conversionsteps. An up-converted signal is then produced to a high pass variablegain amplifier module 532 which produces an amplified and high passfiltered signal to power amplifier 536 for transmission as an outgoingradio frequency signal.

One aspect of the embodiment of FIG. 16 is that transmitter 500 includesan analog gain and filter control module 540 that is operable to producegain and filter control signals to various amplification and filteringmodules of transmitter 500. Specifically, however, analog gain andfilter control module 540 is operable to provide independent filtercontrol signals to I and Q branch filters (here, filters 512 and 520) toprovide differing filter responses for the I and Q branch signalcomponents. As such, complex filtering is produced to createnon-symmetric shaped signal responses. Such complex filtering may alsobe done digitally. If I and Q component signals are digitally filteredin a non-symmetric manner to allow symmetric processing in the analogtransmit path, the I and Q component signals produced by the digitalprocessor are different in magnitude as well as phase even if filteringin the analog transmit paths are symmetric.

It should be understood that such complex filtering may be performed intransmitters having different configurations. Thus, for example, thecomplex filtering illustrated in FIG. 16 may be performed for thetransmitters of FIGS. 2-6 even though the separate I and Q branches arenot explicitly shown Additionally, it should be noted that aspects ofthe methods suggested by FIGS. 6-11 may readily be implemented by any ofthe transmitters of FIGS. 1-5 and 16.

As one of ordinary skill in the art will appreciate, the term“substantially” or “approximately”, as may be used herein, provides anindustry-accepted tolerance to its corresponding term and/or relativitybetween items. Such an industry-accepted tolerance ranges from less thanone percent to twenty percent and corresponds to, but is not limited to,component values, integrated circuit process variations, temperaturevariations, rise and fall times, and/or thermal noise. Such relativitybetween items ranges from a difference of a few percent to magnitudedifferences. As one of ordinary skill in the art will furtherappreciate, the term “operably coupled”, as may be used herein, includesdirect coupling and indirect coupling via another component, element,circuit, or module where, for indirect coupling, the interveningcomponent, element, circuit, or module does not modify the informationof a signal but may adjust its current level, voltage level, and/orpower level. As one of ordinary skill in the art will also appreciate,inferred coupling (i.e., where one element is coupled to another elementby inference) includes direct and indirect coupling between two elementsin the same manner as “operably coupled”.

While the invention is susceptible to various modifications andalternative forms, specific embodiments thereof have been shown by wayof example in the drawings and detailed description. It should beunderstood, however, that the drawings and detailed description theretoare not intended to limit the invention to the particular formdisclosed, but, on the contrary, the invention is to cover allmodifications, equivalents and alternatives falling within the spiritand scope of the present invention as defined by the claims. As may beseen, the described embodiments may be modified in many different wayswithout departing from the scope or teachings of the invention.

1. A method for producing an outgoing radio frequency signal,comprising: selecting a particular signal shape from a signal shapinglogic that has a plurality of signal shapes to produce a plurality ofcorresponding spectral mask densities, wherein the particular selectedsignal shape that generates a particular corresponding spectral maskdensity is based, at least in part, on a signal type and correspondingstandard or protocol, and wherein the plurality of spectral maskdensities that are to be generated at an output of a power amplifiercorresponds to signal shapes that include: a first signal shape havingsubstantially equal power across frequencies of a modulated signal; asecond signal shape having greater power at frequencies proximate to acenter frequency of the modulated signal and reduced power atfrequencies at outer ends of a bandwidth of the modulated signal; and athird signal shape having greater power at frequencies proximate to thecenter frequency of the modulated signal, without regard to spectralflatness, and substantially no power at frequencies at outer ends of thebandwidth of the modulated signal; applying pre-distortion compensationto an outgoing digital data in a digital transmit path to compensate fordownstream distortion introduced in an analog transmit path; generatingcontrol information from the signal shaping logic corresponding to theparticular selected signal shape; applying the control information tocontrol a digital gain to adjust gain of the outgoing digital data afterpre-distortion compensation in the digital transmit path and to controlanalog gain and filtering in the analog transmit path, includingseparate in-phase (I) and quadrature (Q) filtering control in I and Qbranches of the analog transmit path to generate non-symmetric amountsof power to frequencies at the outer ends of the bandwidth of themodulated signal; and producing the particular corresponding spectralmask density at the output of the power amplifier for transmission ofthe modulated signal.
 2. The method of claim 1, wherein when applyingreduced power to the outer ends of the bandwidth includes applying up toa maximum allowed power to frequencies proximate to the center frequencyof the modulated signal and applying reduced power to frequencies thatare a defined distance from the center frequency, but still within thebandwidth of the modulated signal.
 3. The method of claim 2, wherein thereduced power is within a specified amount of the power produced atfrequencies proximate to the center frequency.
 4. The method of claim 1,wherein the non-symmetric amounts of power are provided to frequenciesfarthest from the center frequency of the modulated signal, with lowestfrequencies having less power than highest frequencies for the modulatedsignal.
 5. The method of claim 1, wherein when generating non-symmetricpower, complex filtering is used to produce lower amounts of power tolow frequency end in relation to high frequency end of the bandwidth ofthe modulated signal.
 6. A method for producing an outgoing orthogonalfrequency division multiplexing (OFDM) radio frequency signal,comprising: selecting a particular signal shape from a signal shapinglogic that has a plurality of signal shapes to produce a plurality ofcorresponding spectral mask densities, wherein the particular selectedsignal shape that generates a particular corresponding spectral maskdensity is based, at least in part, on a signal type and correspondingstandard or protocol, and wherein the plurality of spectral maskdensities that are to be generated at an output of a power amplifiercorresponds to signal shapes that include: a first signal shape havingsubstantially equal power across frequencies of a modulated signal; asecond signal shape having greater power at frequencies proximate to acenter frequency of a modulated signal and reduced power at frequenciesat outer end of a bandwidth of the modulated signal; a third signalshape having greater power at frequencies proximate to the centerfrequency of the modulated signal, without regard to spectral flatness,and substantially no power at frequencies at outer ends of the bandwidthof the modulated signal; applying pre-distortion compensation to anoutgoing digital data in a digital transmit path to compensate fordownstream distortion introduced in an analog transmit path; generatingcontrol information from the signal shaping logic corresponding to theparticular selected signal shape; applying the control information tocontrol a digital gain to adjust gain of the outgoing digital data afterpre-distortion compensation in the digital transmit path and to controlanalog gain and filtering in the analog transmit path, includingseparate in-phase (I) and quadrature (Q) filtering control in I and Qbranches of the analog transmit path to generate non-symmetric amountsof power to frequencies at the outer ends of the bandwidth of themodulated signal; and producing the particular corresponding spectralmask density at the output of the power amplifier for transmission ofthe modulated signal.
 7. The method of claim 6, wherein the modulatedsignal of the outgoing OFDM radio frequency signal comprises specifiedOFDM sub-carriers.
 8. The method of claim 7, further includinggenerating pre-distortion compensation signals in the digital transmitpath at in-band frequencies to counteract phase or amplitude distortion.9. The method of claim 7, further including selectively applying powerto specified sub-carriers.
 10. The method of claim 9, wherein whenapplying substantially no power to the outer ends of the bandwidthincludes applying up to a maximum allowed power to sub-carrierfrequencies proximate to the center frequency of the modulated signaland applying substantially no power to frequencies that are a defineddistance from the center frequency, but still within the specifiedbandwidth of the modulated signal.
 11. The method of claim 9, whereinwhen applying reduced power to the outer ends of the bandwidth includesapplying up to a maximum allowed power to sub-carrier frequenciesproximate to the center frequency of the modulated signal and applyingreduced power to sub-carrier frequencies that are a defined distancefrom the center frequency, but still within the specified bandwidth ofthe modulated signal.
 12. The method of claim 11, wherein the reducedpower is within a specified amount of the maximum allowed power.
 13. Themethod of claim 6, wherein the non-symmetric amounts of power areprovided to sub-carrier frequencies farthest from the center frequencyof the modulated signal.
 14. The method of claim 6, wherein whengenerating non-symmetric power, non-symmetric amounts of power areprovided to sub-carrier frequencies farthest from the center frequencyof the modulated signal, with lowest sub-carrier frequencies having lespower than highest sub-carrier frequencies.
 15. An integrated circuitradio transceiver operable to support wireless communications,comprising: a digital processor operable to produce outgoing digitaldata; pre-distortion compensation module coupled to apply pre-distortioncompensation to the outgoing digital data to compensate for downstreamdistortion introduced in an analog transmit path; digital gain circuitrycoupled to receive the outgoing digital data after pre-distortioncompensation and to adjust a digital gain of the outgoing digital data;radio front end transmit path circuitry in the analog transmit pathcoupled to the digital gain circuitry, the radio front end transmit pathcircuitry including an up-conversion module, filters, analog gaincircuitry, and a power amplifier operable to produce a modulated signalfrom the outgoing digital data after pre-distortion compensation anddigital gain adjust; and shaping logic circuitry to select a particularsignal shape from a plurality of signal shapes to produce a plurality ofcorresponding spectral mask densities, wherein the particular selectedsignal shape that generates a particular corresponding spectral maskdensity is based, at least in part, on a signal type and correspondingstandard or protocol, and wherein the plurality of spectral maskdensities that are to be generated for transmission corresponds tosignal shapes that include: a first signal shape having substantiallyequal power across frequencies of a modulated signal; a second signalshape having greater power at frequencies proximate to a centerfrequency of the modulated signal and reduced power at frequencies atouter ends of a bandwidth of the modulated signal; and a third signalshape having greater power at frequencies proximate to the centerfrequency of the modulated signal, without regard to spectral flatness,and substantially no power at frequencies at outer ends of the bandwidthof the modulated signal; wherein the shaping logic circuitry to generatecontrol information corresponding to the particular selected signalshape and to couple the control information to the digital gaincircuitry and the radio front end transmit path circuitry to control athe digital gain of the digital gain circuitry, to control analog gainof the analog gain circuitry and to control filtering in the filters,including controlling separate in-phase (I) and quadrature (Q) filtersin I and Q branches of the analog transmit path to generatenon-symmetric amounts of power to frequencies at the outer ends of thebandwidth of the modulated signal, for modulated signal transmissionfrom the power amplifier utilizing the particular corresponding spectralmask density.
 16. The integrated circuit radio transceiver of claim 15wherein the shaping logic circuitry produces the control information forthe third signal shape to apply maximum allowed power to sub-carrierfrequencies proximate to the center frequency and to apply substantiallyno power to sub-carrier frequencies that are a defined distance from thecenter frequency, but still within the specified bandwidth.
 17. Theintegrated circuit radio transceiver of claim 15, wherein the shapinglogic circuitry produces the control information for the second signalshape to apply maximum allowed power to sub-carrier frequenciesproximate to the center frequency and to apply reduced power tosub-carrier frequencies that are a defined distance from the centerfrequency but still within the specified bandwidth, in which the reducedpower is within a specified value in relation to the maximum allowedpower.
 18. The integrated circuit radio transceiver of claim 15, whereinthe shaping logic circuitry causes non-symmetric amounts of power to beapplied to outer most sub-carrier frequencies, when utilizingnon-symmetric power generation.
 19. The integrated circuit radiotransceiver of claim 15, wherein the shaping logic circuitry causesnon-symmetric amounts of power to be applied to frequencies farthestfrom the center frequency of the modulated signal, with lowestfrequencies having less power than highest frequencies for the modulatedsignal, when utilizing non-symmetric power generation.
 20. Theintegrated circuit radio transceiver of claim 15, wherein the modulatedsignal is an orthogonal frequency division multiplexing (OFDM) radiofrequency signal.